Method and apparatus for radio ranging



Aug. 26, 1947. H. M. HART METHOD AND APPARATUS FOR RADIO HANGING Original Filed March 20-, 1941 3 Sheets-Sheet l mQQjGmO 5533mm Aug. 26, 1947. H. M. HART METHOD AND APPARATUS FOR RADIO HANGING 3 Sheets-Sheet 2 Original Filed March 20, 1941 FIG. 5

INVENTOR. HAROLD M. H RT H. M. HART 2,4265% METHOD AND APPARATUS FOR RADIO HANGING Original Filed March 20, 1941 5 Sheets$heet 3 Patented Aug. 26, 1947 UNlTD METHOD AND APPARATUS FOR RADIO RANGING Harold M. Hart, Cambridge, Mass, assignor, by

mesne assignments, to Submarine Signal Company, Boston, Mass, a corporation of Delaware '20 Claims.

i The present application is a division of my copending application Serial No. 384,353, filed March 20, 1941.

The present invention relates to radio echo ranging systems, and more particularly to methods and apparatus for producing an electromagnetic wave impulse, synchronizing the production of the same with an indicating device and for indicating received signals.

It has heretofore been proposed to transmit a short electromagnetic wave impulse and to measure the time interval elapsing between the emission of the impulse and the receipt of an impulse or echo reflected from an object whose distance is to be determined. It has also been proposed to employ a cathode ray tube to indicate the receipt of a reflected impulse and to measure the time interval between the transmitted and reflected impulses, thereby obtaining a measure of the distance.

It is an object of the present invention to provide improved methods and apparatus for radio echo ranging.

It is a further object of the present invention to provide improved methods and apparatus for generating an electromagnetic wave impulse of suitably short time length and high power and to maintain a high degree of accuracy in the length of the time interval between periodically emitted impulses.

A further object of the invention is to provide an improved cathode ray tube indicator and further to provide such an indicator in which the cathode ray beam is subjected to a field tending to cause the beam to produce a truly circular trace on the fluorescent screen.

A further object of the invention is to provide a method and apparatus whereb the production and emission of the wave impulse can be accurately synchronized with the beam-rotating field of the cathode ray tube and moreover whereby the emission of the impulse can be made to occur at any desired instant with respect to the cathode ray beam rotating field.

A further object of the invention is to provide a cathode ray tube indicator whose full-scale range can conveniently be varied.

The above and other objects of my invention will best be understood from the following de scription taken in connection with the accom panying drawings in which Fig. 1 is a schematic diagram of the circuits and apparatus involved in the invention; Fig. 2 is a front elevation of the cathode ray tube indicator scale which is shown in vertical section in Fig. 1; Fig. 3 is a graph illustrating features of the invention; Fig. 4 is a schematic diagram of a form of frequency multiplier used in Fig. 1; Figs. 5 and 6 are further graphs illustrating features of the invention; Fig. '7 is a schematic diagram of a modification of a portion of Fig. 1; and Figs. 8 and 9 are schematic diagrams of modifications of the keying circuit shown in Fig. 1.

A suitable form of my invention is shown in Fig. 1 0f the drawing in which in general a cathode ray tube indicator is provided with a deflecting field tending to cause the cathode ray beam to produce a circular trace on the fluorescent screen at a suitable predetermined speed of rotation corresponding to the frequency or a multiple of the frequency of an alternating current generated by a suitable oscillator. This same alternating current brings about a periodic discharge of a condenser through a gaseous discharge tube to permit another oscillator to energize a transmitting antenna for a short period of time in each cycle of the controlling frequency. The reflected wave is received and caused to produce an indication by means of a cathode ray tube.

More specifically the system is as follows: A cathode ray tube I is provided with a fluorescent screen 2 adjacent which there may be arranged a scale 3 calibrated in units of distance. The cathode ray tube is also provided with cathode, grid and anode electrodes 4, 5 and 6, respectively, and coils l and 8 for producing a suitable magnetic field for deflecting the cathode beam. In place of the coils 'l and 8 electrostatic deflecting electrodes may, of course, be used as is well known in the art, but I prefer to use a magnetic deflecting field because of the ease of controlling the cathode beam in accordance with a feature of my invention as hereinafter described. The coils l and 8 are energized fro-m a sweep circuit in such a Way as to cause the cathode beam to produce a circular trace on the fluorescent screen adjacent to the scale 3 when the grid 5 is sufficiently positive to permit the beam to pass to the screen.

For generating the rotating field and synchronously controlling the periodic transmission of signal impulses an oscillator 9 and amplifier iii are provided which produce an alternating current having a frequency equal to the desired rate of emission of successive periodic signal impulses, for example, a frequency of 5000 cycles per second. This current is fed into the primary ll of transformer 12 having a secondary winding l3 which is connected to a sweep circuit 83. The sweep circuit 83 comprises a condenser l5 and a resistance It connected in series and through contacts 5I and 50 of a four-pole three-position switch 55 in series with the deflecting coil I and thence through ground back to the transformer secondary I3. In parallel with this circuit is another similar series circuit comprising a condenser I1 and a resistance I8 connected in series and through contacts 6! and 50 of switch 55 in series with the other deflecting coil 8 and through ground back to the secondary I3 of transformer I2. The currents through the two deflecting field coils are in quadrature with each other. Each of these deflecting circuits is tuned to resonance by means of the condensers. By doing this, all harmonics are eliminated so that the traces of the cathode ray will be smooth, symmetrical figures. Furthermore, with this arrangement there is no necessity for using a high grade class A amplifier at I!) as has heretofore been required. By varying the values of resistance in these two circuits, currents of the proper amplitude and phase relation can be made to pass through the coils I and 8 whereby the normal trace of the cathode ray beam on the fluorescent screen 2 can be made to be a true circle of the desired diameter. Having determined the proper values, the condensers and resistances may, of course, be fixed in magnitude.

The cathode beam is thus caused to tend to rotate at the same frequency as that of the keying frequency oscillator. Since a frequency of beam rotation of 5000 revolutions per second corresponds for echo ranging to a full scale reading of 18.5 miles on the scale 3, short distances may not be ascertained with sufiicient accuracy. If the keying frequency is less than 5000 revolutions, the condition becomes even worse. It may, therefore, often be desirable to expand the scale of the indicator by changing its range. It is, however, necessary at the same time to preserve synchronization between the rotation of the oathode beam and the transmission of the signal impulses. This can, of course, be accomplished simply by increasing the keying frequency and using the increased keying frequency to control the cathode beam sweep as with the lower frequency. It often happens, however, that it is inconvenient or diflicult, if not impossible, to increase the keying frequency while at the same time maintaining the necessary accuracy in signal length and time interval between successive signals at the desired power output.

The present invention makes possible the changing of the range of the indicator without any change in the impulse transmission rate. In other words, the keying rate of the high frequency oscillator may be made much lower than the rate of rotation of the cathode beam of the indicator. Thus, the indicator can be read to a greater accuracy than if the cathode beam were rotated at the same frequency as the periodic impulse transmission frequency, as was heretofore necessary in this type of radio echo distance measuring systems. However, since this arrangement results in the transmission of signals at a lower rate than the rate of rotation ofthe cathode beam, so that a signal may be transmitted in, say, only every alternate or every fourth revolution of the cathode beam, a further feature of the present invention prevents the operation of the cathode beam indicator by noise and/or sig nals during the unused revolutions ofthe beam deflecting field by completely suppressing the beam during such revolutions.

To this end one or more frequency multipliers energized from the keying frequency oscillator are used to produce alternating currents of the proper frequency to rotate the cathode beam at the desired speed. Simultaneously rectified impulses of the proper frequency and polarity are impressed upon the grid of the cathode ra tube indicator to suppress the beam at the proper intervals.

As illustrated, a four-pole, three-position switch 55 operated by the switch bar 56 is provided to make the proper connections for the changes in the range of the indicator. Ihe switch 55 comprises four movable brushes 55, 59, and I00, respectively, each adapted to make contact with three stationary studs as shown.. Thus, as illustrated in the drawings, the switch is in its initial position, the brush 50 being connected to stud 5! and the brush 60 to stud BI whereby the deflecting field coils I and 8 of the cathode ray tube I are energized to rotate the cathode beam at a rate equal to the keying frequency. Under these conditions the brushes 9i! and I00 are respectively connected to studs SI and I0! which are not connected to anything therefore these two poles of the switch are inactive in this position.

In the second position of the switch the brush Ellis connected to stud 52, brush 50 to stud 52, brush 90 to stud 92, and brush I00 to stud I02. Stud I02 is dead so that this part of the switch is inactive. In this second position of the switch energy of the keying frequency as produced in the secondary I3 of the transformer I2 is conducted by lead 55 through stud 92 and brush 90 of the switch 55 to the input terminal 55 of a frequency multiplier 68 which in this case is a frequency doubler. Energy of the keying frequency is also applied to a diode rectifier 55 through a phase-adjusting circuit comprising a series condenser 94 and an inductance 05 and a resistance 91. The cathode of the rectifier is connected to the condenser 94 while the anode of the rectifier is connected through a resistance 58 to ground. A conductor 99 leads from the anode of the tube through a resistance 54 to the grid 5 of the cathode ray tube indicator I. The output of the frequency multiplier 68 is connected through the sweep circuit 84 which, like the sweep circuit 83, comprises two suitable seriesconnected resistance and condenser combinations. One of these is connected to the stud 52 of the switch 55 and thence by way of brush 50 to the deflecting coil I, and the other is connected to the stud 62 and through brush 50 to the other deflecting coil 8. Thus, assuming the output of the frequency multiplier 58 to be twice the keying frequency, the deflecting coils l and 5 will produce a beam-deflecting field, tending to rotate the beam at twice the keying frequency. Since, however, the grid 5 of the cathode ray tube is energized with a negative potential produced by the passage of the negative half cycles of the keying frequency through the diode 95, the oathode beam will be completely suppressed during every alternate revolution of the beam-deflecting 7 field produced by the coils I and 8, that is during the non-keying revolutions.

In connection with this suppression of the cathode beam it should be noted that the cathode of the indicator tube I is connected to a resistance'82 and battery 88 to ground. The potential provided by the battery 88 initially biases the grid 5 negatively with respect to the cathode so that a partial suppression of the cathode beam is obtained whereby its trace on the fluorescent screen 2 is made to be quite dim. When there is no other beam-suppressing potential on the grid 5, signal energy-received on the antenna 86- and passed by the receiver I 04 to the grid 5 of the indicator will make the grid sufficiently positive so as to overcome the initial negative bias provided by the'battery 88 and produce a bright indication in the form of a bright spot on the screen 2. However, when the switch 55 is in its second position so that the deflecting field rotates the beam at twice the keying frequency, the grid 5 will-be made highly negative by the potential provided by diode 95 during every alternate revolution' of the-cathode beam and thus the latter will'be completely suppressed during these alternate revolutions and no indications will be produced in responseto signals picked up by the antenna. beam the keying frequency will, however, be in its positive half cycle, at the beginning of which it will actuate the high frequency impulse transmitter; as further explained below. None of the positivehalf cycles of the keying frequency will, however, be passed by the diode 95 so that the grid 5 of the cathode ray tube indicator will only beslightly negative-as determined by the bias provided by the battery 88. The indicator tube I is therefore in condition to produce an indication if an echoor other signal should be received by the receiver ltd during these positive half cycles of the keying-frequency. Thus, for the second position of switch 55, the full-scale range of the indicator is one-half of its range in the first switch position.

In thethird-position of the switch 55, brush 59 will be connected to stud 53, brush iii to stud 63, brush 9!! to stud $3 and brush we to stud I03. The studs 92 and 93 are connected together so that in the third position cf'the switch the frequency multiplier 68 will still be active as will the diode 95. Some of the energy from the multiplier 68 is conducted by the lead 185 through stud I63, brush it and lead N36 to a second frequency multiplier 8!. In the present case this also i a frequency doubler whose output will thus be four times the frequency of the keying frequency oscillator. The output of multiplier 8i is fed through a sweep circuit 85 which again is similar to the sweep circuit 83 and composed of two series-connected resistance and condenser combinations of the proper magnitude for the frequency in question. One of these resistance- Duringthe other revolutions of the condenser combinations is connected through the stud 53 and brush 59 to the deflecting-field coil 7 of the cathode ray indicator, while the other is connected through stud E3 and brush 6!] to the other deflecting-field coil 8. The magnetic defleeting field is therefore such as to tend to rotate the cathode beam at four times the key n frequency. Since, a will be further explained below, a high frequency signaling impulse is transmitted at the beginning of each cycle of the keying frequency, there will be an impulse transmitted at the beginning of every fourth revolution of the cathode beam. In the two revolutions of the cathode beam just preceding thetransmission of a signal impulse, the grid 5 of the cathode ray indicator will be biased negatively so as completely to suppress the beam since the diode 95 is still operative when the switch is in the third position.

It is desired, however, also to prevent stray signal indications in the second revolution of the cathode beam following the revolution at the beginning of which the ranging signal impulse is transmitted. To this end another diode I01 is provided which functions. in substantially the same manner as the diode 95.1 It is energized, however, by the output of the freuqency multiplier B8 isoithat .it will pass current during each negative half cycle of the output of the multiplier 68. The cathode of the diode i0! is connected to .the multiplier 63 by way of lead I05, switch stud Hi3, brush Hill, lead 806 and a phaseadjusting circuit comprising a condenser I08, an inductance I09 and 'a resistance H0. The anode of the diode, I0! is connected through a resistance Ill to-ground. A conductor H2 joins the anode to theconductor 99 which leads to the grid 510i the cathode ray tube l. The diode Hi1 is-thus connected in parallel with the diode 95. The grid 5 of the cathode ray indicator l is thereforeprovided with a beam-suppressing potential during both the. negative half cycles ofthekeying frequency and during the negative half cycles of twice the keyingfrequency, produced by the multiplier 68; The grid 5 is therefore sufficiently positive to enable the cathode beamto produce an indication only during every fourth complete cycle of the frequency produced by the multiplier 8| and this complete cycle corresponds to the first half of the positive half cycle of the. keying frequency at the beginning of which ahigh frequency signal impulse is emitted. Thus, for the third switch position the full-scale range of the indicator is one-fourth its range in the first switch position.

The relative time intervals involved can be visualized from Fig. 6 which represents a graph of one cycle of the keying frequency f1, two cycles of the output of multiplier 68 designated as 2h and'four cycles of the output of multiplier 8| designated as 4h. The positive half cycle of the keying frequency f1 occupies the time interval t3 and the negative half cycle occupies the time interval 154. Itisat the beginning of the time interval is that the high frequency ranging signal impulse is transmitted. In the first position. of switch 55, which is that shown in Fig. 1,

the cathode beam isrotated in synchronism with the frequency f1 30 that the indicator will be active to indicate received impulses during the entire'cycle of the keying frequency, namely during both 173' and t4. Iirthe second position of switch- 55rthe cathode beam isrotated insynchronism with the frequency 2h and the high frequency-ranging impulse'is transmitted at the beginning of the first positive'half cycle of this frequency; namely "at the beginning of the interval. ts as before. The beam of the cathode ray indicator is, however, suppressed during the negative half cycle of the frequency f1, namely during'the' interval t4 so that the cathode ray-indicator is active only during one complete cycle of theifrequency 2h, namely the interval is. In

the third switch position the cathode beam is rotated in synchronismwith the frequency M1. The cathode beam in thi case is suppressed not only during the interval t4 but also during the interval is which corresponds to the first negative half'cycle-of the frequency 2h. The indicator is therefore active only during the first complete cycle ofthe frequency J1. In Fig. 6, the various phases have'been adjusted to be as shown by adjustment of the resistor 31, 91 and I I0.

While it-isdesirable, as above described, to make the cathode ray indicator inactiv during the cathode beam revolutions in which no signal is transmitted-it will be understood by those skilled in -the art that it is not essential to do this and that the diodes 95 and 107 may, therefore, be omitted, if desired. Further, if such beam suppression is not to be used, it will not be necessary to make the frequency multipliers 6B and 8| in the form of frequency doublers but odd harmonic multipliers could be used if desired. I prefer, however, to make the frequency multipliers in the form of doublers and to use them in combination with the beam-suppressing circuits as described. While I have shown only two cascaded frequency multipliers providing three different ranges for the cathode ray indicator, it will be understood that more than two can be used providing as many ranges as may be desired and also providing automatic beam-suppressing action during the unused revolutions of the cathode beam.

Suitable-forms of frequency multipliers or of frequency doublers are well known in the art. For purposes of illustration, however, a conventional push-push type of frequency doubler is diagrammatically shown in Fig. 4. The original frequency ii is fed into the primary 69 of transformer 79 having center-tapped secondary H. The transformer primary is tuned by condenser 12 and the secondary by condenser 13. Resistors l4 and 15 are shunted across the two halves of secondary H, as are also condensers 16 and 11 which serve as a low impedance path for any second harmonic present in the input circuit. Two triodes l8 and 19, operating as a push-push doubler, have their cathodes connected together and to the center tap of secondary l I, while their grids are respectively connected to the extremities of secondary H. The anodes of the triodes ar connected together and through inductance 80, which may form the primary of the input transformer for a second stage of multiplication, to the positive terminal of the anode voltage supply. The inductance 80 is tuned by condenser 8! to the second harmonic of the input frequency. Thus, there is produced a frequency of twice the input frequency.

For the synchronous production of a high frequency ranging impulse, a portion of the current produced by the keying frequency oscillato in the secondary I3 is also fed into the primary H! of a transformer 20 having a secondary winding 21 for the control of the keyingor impulse-transmitting circuit. This includes an oscillator tube 22 which may be a more or less conventional high frequency three-electrode vacuum tube oscillator with suitable control and output circuits or it may be an oscillator of the velocity modulation type or any other desired type of electromagnetic wave generator. As illustrated in Fig. 1, the oscillator comprises a modified Colpitts type circuit having a three-electrode vacuum tube 22 whose anode circuit includes an inductive choke 23 and voltage source 24 shunted by a bypass condenser 25. The anode output circuit includes a tuned tank circuit 26 comprising condenser 21 and inductance 28 which may be the primary of an output transformer having a secondary winding 29 connected to an antenna 30 and ground. The tank circuit 26, in addition to being connected to the anode 3! of the tube 22, is also connected through a series blocking condenser 32 to the grid 33. The input circuit of the tube 122 comprises a resistance 34 connected in series with a battery 35 and a high frequency choke 49 between the grid and cathode of the tube. The battery 35 is adjusted to maintain the grid 33 at a potential just sufiicient to prevent oscillation voltage is applied between the grid and cathode of the tube 22 obtained from an impulse-producing circuit which, in turn, is controlled by the keying frequency oscillator 9.

The impulse-producing circuit comprises a gaseous discharge tube 31 having a cathode 38, grid 39 and anode A0. The anode 48 is connected through series resistance 41 to the positive terminal of a suitable direct current source 42. The anode 40 is also connected through a condenser 43 and a variable series resistance 44 to the oathode 38. The junction of the condenser 43 and resistance 44 is connected to the negative terminal of the source 42. The condenser 43, which is charged from the direct current source through resistance 4|, thus supplies electric energy which is discharged through the resistance 44 when the tube 31 becomes conductive. The grid 39 is connected to the cathode 38 by means of a resistance 46. The voltage of the secondary 2| of the transformer 20 is impressed across the resistance 46 through a phase-shifting circuit which comprises the series condenser 45 and a variable resistance 47 which is connected in series with an inductance 48, the resistance and inductance together being shunted across the secondary 2|. The voltage drop across resistor 44 due to the condenser discharge through the tube is impressed on the grid 33 of the high frequency oscillator 22 through the cathode ground connections and blocking condenser 89 and high frequency choke 49 which has a low impedance to the keying impulse. The time length of the keying impulse is determined by the time constant of the discharge circuit formed by condenser 43 and resistor 44.

The operation is as follows. quency produced by the oscillator 3 is, with switch 5! in the position shown in Fig. 1, impressed upon the cathode ray tube coils to produce a rotating deflecting field forthe cathode ray beam in the tube l. The same frequency is also impressed upon the grid 39 of the tube 31 in a relative phase, depending upon the values of condenser 45, resistance 47 and inductance 48. By varying the magnitude of resistance 4'! the phase relation between the voltage applied to the grid 39 and the voltages applied to the deflecting coils l and 8 for the first position of switch 55 can be controlled. By this means the particular instant of emission of the signal impulse with regard to the instantaneous position of the cathode beam as determined by the field produced by the deflecting coils l and 3 can be controlled. The system can, therefore, readily be adjusted so that the signal is transmitted exactly at the instant the cathode ray is at the zero point of the scale 3, and this is true regardless of the cathode beam rotation frequency. When the switch 55 is in its second position so that the cathode beam is rotatin at twice the keying frequency, the particular instant of emission of the signal im ulse with reference to'the instant at Which the cathode beam is at the zero position of the scale is likewise controlled by varying the magnitude of resistance 41. In this case it is also necessary, however, to control the relative time phase in which the beam-suppressing potential is applied to the grid 5. This is accomplished by varying the resistance 5? in the phase-shifting circuit of the diode 35. A similar control is provided for the third switch position in the variable resistance I ID in the circuit of the diode IE1. By these latter adjustments it is possible to remove the beam-suppressing action at any desired time before the emission of the next signal impulse. In

The keying fre-,

other words, the relative phases of the various frequencies represented in Fig. 6 can be shifted. In any case, however, the instant of emission of the signal impulse remains independently controllable.

The tube 3'! is of the gaseous discharge type wherein the fiow of current between the cathode and anode can be commenced with a given anode Voltage only by applying a sufliciently positive voltage to the grid, but current fiow having once commenced, will continue until the anode voltage is reduced to a relatively low value even though inthe meantime the grid may have attained a potential below the critical potential required to initiate the discharge. This type of tube is used because not only is it relatively easy therewith to produce a high current discharge but also becaus it is unnecessary, in order to maintain the discharge, to continue to supply potential for a current flow between the grid and the cathode. Only a very small initial grid current need, therefore, be supplied and consequently very little power need be furnished b the control circuit. Most gaseous discharge tubes, however, have a relatively long deionization time which means that with decreasing anode voltage, the current flow through the tube will not rapidly fall to zero when a definite value of anode voltage is reached, but will too gradually taper off to zero even though the grid may have in the meantime been reduced to a potential below the critical potential.

Such tubes are not satisfactory, but tubes with a deionization time short compared to the time between successive impulses should be chosen, e. g. a mercury vapor tube such as the type General Electrical FG 657 which will deionize soon enough to give condenser 43 time to recharge fully before the next impulse is to be emitted. Also the internal resistance of the tube chosen must drop rapidly with beginning of discharge so that the discharge current will produce a steep wave front voltage impulse on the grid of the oscillator tube.

A further requirement of the system is that the impulse must always start within a time short compared to the time length of the impulse. This is necessary for accuracy since the time interval and the distance measurement is made from the beginning of the transmitted impulse to the beginning of the reflected impulse. The discharge in gaseous tubes, however, does not always start at precisely the same value of grid potential even with constant alternating potential, but there is always a range of grid potential somewhere within which the tube will be sure to fire. According to the present invention the necessary accuracy is obtained by sweeping the gaseous tube grid voltage through the region of critical grid potential within which discharge will commence within the required short time interval.

To make all this more clear conside a specific example. Let us assume that the keying frequency oscillator 9 is tuned to 5000 cycles. The grid of gaseous tube 31 will then become positive and render the tube conductive 5000 times per second. Similarly the oscillator will transmit to antenna 30 an impulse 5000 times per second. The time interval between successive impulses is therefore 0.0002 second. The cathode beam of indicator I for the switch position shown will then tend to move in a circula path at the rate of 5000 revolutions per second. Since electromagnetic waves travel approximately 186,000 miles per second, the maximum distance which 10 can be measured is equal to a distance from the ranging apparatus corresponding to one half the distance travelled by a wave impulse in 0.0002 second or 1sco00; 0.0o02 6 miles which will be the full scale calibration of scale 3. If the time length of the transmitted impulses be held to one microsecond, the nearest object from which a reflection can be indicated will be approximately 0.2 mile. To keep the possible error in the distance measurement below $0.05 mile, each transmitted impulse must start at the same time in each measuring cycle within :0.000,000,5 second. In other words, in accordance with the invention, it is necessary to sweep the gaseous tube grid voltage through the critical grid voltage region within which the tube may fire in not more than 0.000,001 second, or one microsecond. This is readily accomplished as above described. In fact, if the gaseous tube chosen will positively fire within a critical grid voltage range of, say, one volt and the 5000 cycle voltage has a maximum value of 250 volts, it can readily be shown that the tube will fire at the same instant in each cycle within much less than one microsecond. Assuming the keying voltage to be sinusoidal, we can write:

w=21r times the frequency, and t is time in seconds.

Difierentiating, we find that a small element AEg of the grid voltage is:

AEg=wE COS wtAt Now, since for Eg close to zero, cos wi=1, an element of grid voltage near zero AEg will be AEg =wEAt Therefore AE' @E the time required for the grid voltage to traverse the element AEg Hence, under the above conditions where the critical grid voltage region AEg is one volt, the maximum voltage E is 250 and the frequency is 5000 cycles per second 1 At m=0.000,000,l28 second Thus there results considerably less than the possible error of 0.05 mile above specified. Therefore, alternatively, a lower voltage or a lower frequency may be used. In fact, the frequency may theoretically be reduced to 640 cycles with the specified accuracy. For a lower frequency, the maximum grid voltage must be increased if the required accuracy is to be obtained, or a discharge tube must be used whose critical grid voltage region is smaller than one volt.

Another way of increasing the accuracy of production of the keying impulse is to control the aseous tube grid not by means of a sine wave, but by the use of some other periodic wave, which may be derived from the oscillator 9, and which has a higher rate of change in a, positive direction than a sine wave of the maximum allowable magnitude. For example, a wave of the type shown in Fig. 5 could be used.

It will be understood that transmitting oscillators other than the particular circuit shown in the drawing can be used with my keying circuit. It should be noted, however, that in order to be able to receive and indicate impulses close in time tothe transmitted impulses which may be reflected from nearby objects, it is necessary to keep the time length of the impulses short, This is a feature of the transmitting oscillator circuit shown in Fig. 1 due to the provision of bias battery 35 and resistor 34 which are adjusted to such values that the tube will stop oscillation within a time short compared to the time length of the impulse. Thus the keying impulse provided by the gaseous tube circuit will, due to it steep wave front, rapidly throw the transmitter tube 22 into oscillation and the transmitter tube, due to its bias adjustment, will rapidly stop oscillating when the current through the tube 3'! stops.

These conditions may be visualized from Fig. 3 which is a graph wherein times are plotted as abscissae and signal intensities as ordinates. This graph is diagrammatic only and is not intended as a representation of accurate or even of relative values. The curve 5? indicates the sine wave frequency produced by the keying frequency oscillator 9. The curve 58 represents the envelope of the high frequenc signal impulses produced by oscillator 22 in response to the keying impulses produced by the discharge of condenser 43 through the gaseous tube 31. The condenser discharge current may be somewhat as shown by the curve 59. As discussed above, the time interval t2 between successive impulses 58 is maintained with a high degree of accuracy by the use of a gaseous discharge tube whereby a steep wavefront keying impulse is obtained and by sweeping the control grid voltage of the gaseous tube through its critical. grid potential region in a time short compared to the time length ii of the signal impulse. The

time length 151 of signal impulse depends upon the time constant of the discharge circuit and upon the bias applied to the control electrode of the oscillator. To this end the oscillator grid 33 is biased sufficientl far negative so that it will not oscillate by bias battery 35 and bias resistor 34. When the steep-sided impulse 59 is applied to the grid 33 of the oscillator, the grid 33 is very rapidly driven positive to the point of oscillation and is maintained in the region of oscillation until the steeply descending side of the positive keying impulse 50 allows the bias supply 35 again to stop oscillation. Evidently, by adjusting either or both the discharge circuit time constant and the negative bias 35, the time length ii of the high frequency impulse may be adjusted. It is preferable to keep this time t1 short so that objects close to the transmitter can be ranged. By this means it has been possible to produce high frequency impulses a fraction of a microsecond in duration.

My keying circuit described above can also be used with other types of high frequency osci1la tors. It may, for example, be used with an oscillator of the velocity modulated type such as is schematically shown in Fig. '7. In this type of oscillator an electron beam is produced by a cathode I20 within a sealed envelope I2 I. The cathode beam is controlled by a beam modulating element such as a grid I22 and passes through the center of a pair of doughnut-shaped resonators I23 and I24 to a collector I25. The normal path of the cathode beam is indicated by the dotted line I26 in Fig. '7. The passage of the cathode beam through the tube brings about high frequency oscillations within the resonators I23 and 124. These are connected to each other by a conductor I21 mounted concentrically within the tube I28.

I High frequency energy is conducted from the resonator I24 to the antenna by means of a similar shielded conductor I29. The beam modulating element I22 may be such as to bring about complete suppression of the cathode beam when biased below a critical potential and to permit passage of the beam at all higher potentials. The modulating element I22 may, therefore, be negatively biased by a battery I3! connected in series with resistance I32.

This oscillator replaces the oscillating circuit shown in Fig. 1 and may be connected to the keying circuit through condenser 89. If the beam modulating element is of the type which draws current, then a series resistance I33 should be included in the circuit to provide poor regulation so that the modulating element will not seriously reduce the beam current. On the other hand, if the modulating element is of the cylindrical focussing type sometimes used, the resistor I33 will be unnecessary, for then the beam will be turned full on within a critical range of voltage. My keying circuit then produces an impulse which passes through this range within a sufficiently short time to insure the necessary accuracy in the beginning of the high frequency signal impulse. Similarly the cathode beam will be turned oil within a corresponding critical voltage range which is likewise swept through in the required short time by the descending side of my keying impulse. Thus, also, by the use of a velocitymodulated type of oscillator actuated b my keying circuit, high frequency impulses of the required accuracy of starting and stopping can readily be obtained.

Fig. 8 shows a modification of my keying circuit which is particularly valuable for use in connection with low impedance circuits, for example, for keying an oscillator which has a low impedance at the keying point. The charging resistor 4| in Fig. 1 serves two purposes: First, it enables the condenser 43 to be charged from the direct current source; second, when the gaseous tube 31 discharges, the resistor 4I serves to prevent the charging voltage from maintaining ionization in the gaseous tube. Thus, there is a definite limit to the size of condenser 43 which can be used, and a corresponding limit to the power in the keying impulse which is obtained; for if the size of the condenser be increased, the magnitude of the charging resistance must be decreased in order to charge the condenser fully within the desired short time interval between successive impulses. This reduced magnitude of the charging resistance may, however, prevent the gaseous tube from deionizing.

As shown in Fig. 8 a larger condenser can, however, be used and a larger impulse obtained without sacrifice either of accuracy or of rapidity of the pulses by using a triode vacuum tube I40 in place of the charging resistor. The tube I40 has its anode I4I connected to the positive side of the direct current supply and its cathode I43 to the condenser 43. The grid I42 of the triode is excited'from the same source as the grid of the gaseous discharge tube 31, but with a phase reversal of To this end the grid I42 and cathode I43 of tube I40 are connected across an additional secondary winding I5I provided on transformer 20. It will be evident now that the grid I 42 of the triode I40 will be positive while the grid 39 of the gaseous tube 31 is negative. The triode Hi therefore acts as a low impedance during this period for the passage of charging current for the condenser 43. On the other hand, when the grid 39 becomes positive, resulting in the discharge of condenser 43 through the tube 31, the grid I42 of the triode I40 will be negative so that the triode acts as a high impedance between the condenser-charging source and the gaseous tube 37. The gaseous tube 31 consequently has ample time to deionize before the condensercharging cycle again begins. It will be understood by those skilled in the art that the triode M0 may be used either in the positive side or the negative side of the line. Otherwise than as described, the circuit of Fig. 8 is the same as that shown in Fig. 1, the load to which the keying impulse is to be applied being connected between the cathode 38 and the ground with the interposition of the blocking condenser 89.

An example of its use on the negative side of the line is shown in Fig. 9. This arrangement also has some further advantages. In this case the triode I48 has its cathode 143 connected to the negative side of the charging source and its anode Ml connected to the condenser 43. The grid cathode circuit of the triode I50 is again connected to an additional secondary winding ll on the transformer 28 in a polarity to be 180 out of phase with the grid 39 of the gaseous tube 31. The load resistor M is, however, connected between the condenser 43 and the anode 40 of the gaseous discharge tube 31 and the load is connected between the junction of the condenser 43 and the resistance 45 and ground with the interposition of blocking condenser 89. In this modification as in Fig. 8 the tube I40 presents a low impedance during the charging time of condenser 43 but acts as a high impedance during the discharge of the condenser 43 through the gaseous tube 31. It will be noted, however, that in this case any capacitance which may exist between the cathode 38 of the gaseous tube and ground, as indicated dotted at I52, will now be outside of the condenser discharge circuit. This is of particular importance when the maximum possible magnitude of the keying impulse is required.

Having now described my invention, I claim:

1. In a radio ranging system, a cathode ray tube indicator having elements adapted, when energized, to produce a field for deflecting the cathode beam, means for selectively energizing said elements at any one of a plurality of dif-- ferent frequencies for periodically deflecting the cathode beam over a predetermined path at any one of said frequencies, and means for suppressing the cathode beam during one or more consecutive cycles of said energizing frequencies periodically after a single traverse of said path by the cathode beam.

2. In a radio ranging system, a cathode ray tube indicator having elements adapted, when energized, to produce a field for deflecting the oathode beam, means for selectively energizing said elements at any one of a plurality of different frequencies for periodically deflecting the cathode beam over a predetermined path at any one of said frequencies, each of said frequencies bearing a ratio to the other frequencies in which both denominator and numerator of the ratio are whole integers, one of which is unity, and means for suppressing the cathode beam during one or more consecutive cycles'of said energizing frequencies periodically after a single traverse of said path by the cathode beam.

3. In a radio ranging system, a cathode ray tube indicator having elements adapted, when energized, to produce a field for deflecting the cathode beam, and an element adapted, when energized, to suppress the cathode beam, a source of alternating potential, means for deriving from said source a series of potentials each being twice the preceding frequency, means for energizing said deflecting field producing elements by one of said frequencies for periodically deflecting the cathode beam over a predetermined path at said one frequency, means for rectifying each frequency preceding said one frequency and for applying the rectified outputs to said beam suppressing element.

4. In a radio ranging system, a cathode ray tube indicator having a pair of magnetic deflecting field producing coils for deflecting the cathode beam and means for energizing said coils to rotate the cathode beam in a circle comprising a source of alternating potential of the desired frequency of rotation, a condenser and a resistance connected in series with each other and with one of said coils and across said source, and a second condenser and resistance connected in series with each other and with the other of said coils and across said source.

5. In a radio ranging system, a cathode ray tube indicator having a pair of magnetic deflecting field producing coils for deflecting the cathode beam, means for energizing said coils to rotate the cathode beam in a circle comprising a source of alternating potential of the desired frequency of rotation, a condenser and a resistance connected in series with each other and with one of said coils and across said source, a second condenser and resistance connected in series with each other and with the other of said coils and across said source, and means for varying the magnitudes of said condensers and resistances.

6. In a radio ranging system, a cathode ray tube indicator having a pair of magnetic deflecting field producing coils for deflecting the cathode beam and means for energizing said coils to rotate the cathode beam in a circle comprising a source of alternating potential of the desired frequency of rotation, a condenser and a resistance connected in series with each other and with one of said coils and across said source, and a second. condenser and resistance connected in series with each other and with the other of said coils and across said source, each of said series circuits being tuned to resonance at the frequency of said alternating potential.

'7. In a radio ranging system, means periodically transmitting a signal impulse, a cathode ray tube indicator having a beam-suppressing electrode, means providing a field tending to deflect the cathode beam periodically over a predetermined path at a rate which is the n-th multiple of the rate of impulse transmission where n is any integer, said last-named means including a source of alternating potential, and means for deriving from said alternating potential a beamsuppressing potential repeated periodically at the frequency of signal transmission and having an effective duration of substantially 'Ii-i.

times the interval between successive transmitted impulses, and means for applying the latter potential to said electrode.

8. In a radio ranging system, means periodically transmitting a signal impulse, a cathode ray tube indicator having a beam-suppressing electrode, means providing a field tending to deflect the cathode beam periodically over a predetermined path at a rate which is the n-th multiple of the rate of impulse transmission, where n is any integer, said last-named means including a source of alternating potential, and means for deriving from said alternating potential a beamsuppressing potential repeated periodically at the frequency of signal transmission and having an effective duration of substantially 'rL-l times the interval between successive transmitted impulses, and means for applying the latter potential to said electrode and means for adjusting the time phase of said beam-suppressing potential with respect to the instant of signal transmission.

9. In a radio ranging system, means periodically transmitting a signal impulse, a cathode ray tube indicator, means providing a field tending to deflect the cathode beam periodically over a predetermined path at a rate which is a multiple of the rate of impulse transmission, means for receiving signal impulses and impressing the same upon the tube to tend to produce an indication and means for substantially completely suppressing the cathode beam to prevent the production of an indication even in the presence of received impulses during each cycle of said defleetin field in which no signal impulse is transmitted.

10. In a radio ranging system having a signal impulse transmitter and a cathode ray tube indicator with a scale having a zero position, means for periodically deflecting the cathode beam with reference to said zero position in accordance with a time function, means for operating said transmitter to transmit an impulse periodically at a rate which is equal to said time function, said operating means including a gaseous discharge tube keying circuit adapted when energized to energize said transmitter, mean including a source of alternating potential for periodically energizing said discharge tube, and means for adjusting the time phase of said alternating potential with respect to the periodic deflection of said cathode beam whereby the time of impulse transmission can be synchronized with the cathode beams traverse of said zero position.

11. In a radio ranging system, means periodically transmitting a signal impulse, a cathode ray tube indicator, means providing a field tending to deflect the cathode beam periodicall over a predetermined path at a rate which is a multiple of the rate of impulse transmission, a beam control grid within said tube, means for biasing said grid substantially to suppress the beam, means for receiving signal impulses and impressing the same upon said grid in a direction to overcome said beam-suppressing bias, and means for further biasing said grid completely to suppress said beam even in the presence of received impulses during the cycles of said deflecting field in which no signal impulse is transmitted.

12. In a radio ranging system having a high frequency oscillator tube and circuit, said tube having a control element adapted, in response to an applied potential, to start and stop oscillations in said circuit, a keying circuit adapted to produce periodically potential impulses of peaked wave form, means applying said potential impulses to said oscillator control element, a cathode ray tube indicator with a scale having a zero position, means providing a sweep potential for periodically deflecting the cathode beam with reference to said zero position in accordance with a time function, and electrical means for controlling the phase relation between said peaked potential impulses and said sweep potential whereby the time of impulse transmission can be synchronized with the cathode beams traverse of said zero position.

13. In a radio ranging system having a signal impulse transmitter, an electronic device adapted to produce periodically impulses of peaked wave form, means for impressing said peaked impulses upon said transmitter for the control thereof, an indicator having an indicating element, a source of periodic sweep potential operatively connected to said indicator for the control of the position of said indicating element, and means for controlling the time relation between said peaked impulses and said sweep potential.

14. In a radio ranging system, a high frequency pulse transmitter, a high frequency pulse receiver, means ior producing periodically a keying impulse of peaked wave form for controlling the transmitter to transmit pulses periodically, an indicator having an indicating element for indicating by the position of said element the time interval between transmitted and received pulses, means for applying a potential to said indicator for controlling the position of said element in accordance with a time function and adjustable electrical phase controlling means for adjusting the time relation between said keying impulse and said indicator controlling potential.

15. In a radio ranging system, an indicator having an indicating element, means providing a sweep frequency timing potential operatively associated with the indicating element for controlling the position of the indicating element, means providing a signaling impulse, means providing a peaked potential controlling the emission of the signaling impulse, and phasing means for controlling the phase relation of the peaked potential with respect to the sweep frequency;

16. Ina radio ranging system having a, signal impulse transmitter and a cathode ray tube indicator with a scale having a zero position, means for periodically deflecting the cathode beam with reference to said zero position in accordance with a time function, means for operating said transmitter to transmit an impulse periodically at a rate which is a subharmonic of said time function, said operating means including a gaseous discharge tube keying circuit adapted when energized to energize said transmitter, means including a source of alternating potential for periodically energizing said discharge tube, and means for adjusting the time phase of said alternating potential with respect to 'the periodic deflection of said cathode beam whereby the time of impulse transmission can be synchronized with the cathode beams traverse of said zero position.

17. In a radio ranging system the combination of a cathode ray tube indicator having elements adapted, when energized, to produce a field for deflecting the cathode beam, a sweep circuit for selectively energizing said elements at any one of a plurality of diiferent frequencies for periodically deflecting the cathode beam over a predetermined path at any one of said frequencies, and a beam suppressing circuit connected to said indicator for suppressing the cathode beam during one or more consecutive cycles of said ener- 17 gizing frequencies periodically after a single traverse of said path by the cathode beam.

18. In a radio ranging system the combination of a cathode ray tube indicator having elements adapted, when energized, to produce a field for deflecting the cathode beam, a sweep circuit for selectively energizing said elements at any one of a plurality of different frequencies for periodically deflecting the cathode beam over a predetermined path at any one of said frequencies, each of said frequencies bearing a ratio to the other frequencies in which (both denominator and numerator of the ratio are whole integers, one of which is unity, and a beam suppressing circuit connected to said indicator for suppressing the cathode beam during one or more consecutive cycles of said energizing frequencies periodically after a single traverse of said path by the cathode beam.

19. In a radio ranging system the combination of a pulse transmitter for periodically transmitting a signal impulse, a cathode ray tube indicator, a sweep circuit therefor controlled by said transmitter for providing a field tending to deflect the cathode beam periodically over a predetermined path at a rate which is a multiple of the rate of impulse transmission, a receiver for receiving signal impulses connected to said indicator to tend to produce an indication thereon, and a beam suppressing circuit for said indicator controlled by said sweep circuit for substantially completely suppressing the cathode beam to prevent the production of an indication even in the by said frequency multiplier and producing a source of periodic sweep potential for the control of the position of said indicating element, and a selective control for said frequency multiplier for controlling the time relation between said peaked impulses and said sweep potential.

HAROLD M. HART.

REFERENCES CITED The following references are of record in the file of this patent:

UNITED STATES PATENTS Number Name Date 2,227,598 Lyman et al Jan. 7, 1941 2,178,766 Tolson Nov. 7, 1939 2,246,625 Farnsworth June 24, 1941 2,083,495 Black et a1 June 8, 1937 OTHER REFERENCES RCA Service Notes, Electronic Sweep Oscil- 1ator, and "Cathode-Ray Oscillograph, 1937.

Disclaimer 2,426,501.Har0ld M .'Hart, Cambridge, Mass. METHOD AND APPARATUS FOR RADIO RANGING. Patent dated Aug. 26, 1947. Disclaimer filed Nov. 10, 1950, by the assignee, Rag them Manufactw'z'ng Oompzmy. Hereby enters this disclaimer to claims 10, 12, 13, 14, and 15 of said patent.

[Ofiicz'al Gazette December 5, 1.950.] 

